Orthogonal complex spreading method for multichannel and apparatus thereof

ABSTRACT

An orthogonal complex spreading method for a multichannel and an apparatus thereof are disclosed. The method includes the steps of complex-summing α n1 W M,n1 X n1  which is obtained by multiplying an orthogonal Hadamard sequence W M,n1  by a first data X n1  of a n-th block and α n2 W M,n2 X n2  which is obtained by multiplying an orthogonal Hadamard sequence W 1,n2  by a second data X n2  of a n-th block; complex-multiplying α n1 W M,n1 X n1 +jα n2 W M,n2 X n2  which is summed in the complex type and W M,n3 +jPW M,n4  of the complex type using a complex multiplier and outputting as an in-phase information and quadrature phase information; and summing only in-phase information outputted from a plurality of blocks and only quadrature phase information outputted therefrom and spreading the same using a spreading code.

NOTE: More than one reissue application has been filed for the reissueof U.S. Pat. No. 6,449,306. The reissue applications are U.S. patentapplication Ser. No. 10/932,227, filed on Sep. 2, 2004 and issued asU.S. Pat. No. RE40,385; U.S. patent application Ser. No. 11/648,915,filed on Jan. 3, 2007, which is a continuation reissue application ofU.S. patent application Ser. No. 10/932,227 filed Sep. 2, 2004 now U.S.Pat. No. Re. 40,385; and U.S. patent application Ser. No. 13/177,498(the present application), filed on Jul. 6, 2011, which is acontinuation reissue application of U.S. patent application Ser. No.11/648,915 filed Jan. 3, 2007.

This application is a continuation of application Ser. No. 09/162,764,filed Sep. 30, 1998 now U.S. Pat. No. 6,222,873.

BACKGROUND OF THE INVENTION

1. Field of the Invention

The present invention relates to an orthogonal complex spreading methodfor a multichannel and an apparatus thereof, and in particular, to animproved orthogonal complex spreading method for a multichannel and anapparatus thereof which are capable of decreasing a peakpower-to-average power ratio by introducing an orthogonal complexspreading structure and spreading the same using a spreading code,implementing a structure capable of spreading complex output signalsusing a spreading code by adapting a permutated orthogonal complexspreading structure for a complex-type multichannel input signal withrespect to the summed values, and decreasing a phase dependency of aninterference based on a multipath component (when there is one chipdifference) of a self signal, which is a problem that is not overcome bya permutated complex spreading modulation method, by a combination of anorthogonal Hadamard sequence.

2. Description of the Conventional Art

Generally, in the mobile communication system, it is known that a lineardistortion and non-linear distortion affect power amplifier. Thestatistical characteristic of a peak power-to-average power ratio has apredetermined interrelationship for a non-linear distortion.

The third non-linear distortion which is one of the factors affectingthe power amplifier causes an inter-modulation product problem in anadjacent frequency channel. The above-described inter-modulation productproblem is generated due to a high peak amplitude for thereby increasingan adjacent channel power (ACP), so that there is a predetermined limitfor selecting an amplifier. In particular, the CDMA (Code DivisionMultiple Access) system requires a very strict condition with respect toa linearity of a power amplifier. Therefore, the above-describedcondition is a very important factor.

In accordance with IS-97 and IS-98, the FCC stipulates a condition onthe adjacent channel power (ACP). In order to satisfy theabove-described condition, a bias of a RF power amplifier should belimited.

According to the current IMT-2000 system standard recommendation, aplurality of CDMA channels are recommended. In the case that a pluralityof channels are provided, the peak power-to-average power ratio isconsidered as an important factor for thereby increasing efficiency ofthe modulation method.

The IMT-2000 which is known as the third generation mobile communicationsystem has a great attention from people as the next generationcommunication system following the digital cellular system, personalcommunication system, etc. The IMT-2000 will be commercially availableas one of the next generation wireless communication system which has ahigh capacity and better performance for thereby introducing variousservices and international loaming services, etc.

Many countries propose various IMT-2000 systems which IC require highdata transmission rates adapted for an internet service or an electroniccommercial activity. This is directly related to the power efficiency ofa RF amplifier.

The CDMA based IMT-2000 system modulation method introduced by manycountries is classified into a pilot channel method and a pilot symbolmethod. Of which, the former is directed to the ETRI 1.0 versionintroduced in Korea and is directed to CDMA ONE introduced in NorthAmerica, and the latter is directed to the NTT-DOCOMO and ARIBintroduced in Japan and is directed to the FMA2 proposal in a reversedirection introduced in Europe.

Since the pilot symbol method has a single channel effect based on thepower efficiency, it is superior compared to the pilot channel methodwhich is a multichannel method. However since the accuracy of thechannel estimation is determined by the power control, the abovedescription does not have its logical ground.

FIG. 1 illustrates a conventional complex spreading method based on aCDMA ONE method. As shown therein, the signals from a fundamentalchannel, a supplemental channel, and a control channel are multiplied bya Walsh code by each multiplier of a multiplication unit 20 through asignal mapping unit 10. The signals which are multiplied by a pilotsignal and the Walsh signal and then spread are multiplied by channelgains A0, A1, A2 and A3 by a channel gain multiplication unit 30.

In a summing unit 40, the pilot signal multiplied by the channel gain A0and the fundamental channel signal multiplied by the channel gain A1 aresummed by a first adder for thereby obtaining an identical phaseinformation, and the supplemental channel signal multiplied by thechannel gain A2 and the control channel signal multiplied by the channelgain A3 are summed by a second adder for thereby obtaining an orthogonalphase information.

The thusly obtained in-phase information and quadrature-phaseinformation are multiplied by a PN1 code and PN2 code by a spreadingunit 50, and the identical phase information multiplied by the PN2 codeis subtracted from the identical phase information multiplied by the PN1code and is outputted as an I channel signal, and the quadrature-phaseinformation multiplied by the PN1 code and the in-phase informationmultiplied by the PN2 code are summed and are outputted through a delayunit as a Q channel signal.

The CDMA ONE is implemented using a complex spreading method. The pilotchannel and the fundamental channel spread to a Walsh code 1 are summedfor thereby forming an in-phase information, and the supplementalchannel spread to the Walsh code 2 and the control channel spread to aWalsh code 3 are summed for thereby forming an quadrature-phaseinformation. In addition, the in-phase information and quadrature-phaseinformation are complex-spread by PN codes.

FIG. 2A is a view illustrating a conventional CDMA ONE method, and FIG.2B is a view illustrating a maximum eye-opening point after the actualshaping filter of FIG. 2A.

As shown therein, in the CDMA ONE, the left and right information,namely, the in-phase information (I channel) and the upper and lowerinformation, namely, the quadrature-phase information (Q channel) passthrough the actual pulse shaping filter for thereby causing a peakpower, and in the ETRI version 1.0 shown in FIGS. 3A and 3B, a peakpower may occur in the transverse direction for thereby causingdeterioration.

In view of the crest factor and the statistical distribution of thepower amplitude, in the CDMA ONE, the peak power is generated invertical direction, so that the irregularity problem of the spreadingcode and an inter-interference problem occur.

SUMMARY OF THE INVENTION

Accordingly, it is an object of the present invention to provide anorthogonal complex spreading method for a multichannel and an apparatusthereof overcome the aforementioned problems encountered in theconventional art.

The CDMA system requires a strict condition for a linearity of a poweramplifier, so that the peak power-to-average power ratio is important.In particular, the characteristic of the IMT-2000 system is determinedbased on the efficiency of the modulation method since multiple channelsare provided, and the peak power-to-average power ratio is adapted as animportant factor.

It is another object of the present invention to provide an orthogonalcomplex spreading method for a multichannel and an apparatus thereofwhich have an excellent power efficiency compared to the CDMA-ONEintroduced in U.S.A. and the W-CDMA introduced in Japan and Europe andis capable of resolving a power unbalance problem of an in-phase channeland a quadrature-phase channel as well as the complex spreading method.

It is still another object of the present invention to provide anorthogonal complex spreading method for a multichannel and an apparatusthereof which is capable of stably maintaining a low peakpower-to-average power ratio.

It is still another object of the present invention to provide anorthogonal complex spreading method for a multichannel and an apparatusthereof in which a spreading operation is implemented by multiplying apredetermined channel data among data of a multichannel by an orthogonalHadamard sequence and a gain and, multiplying a data of another channelby an orthogonal Hadamard sequence and a gain, summing the informationof two channels in complex type, multiplying the summed information ofthe complex type by the orthogonal Hadamard sequence of the orthogonaltype, obtaining a complex type, summing a plurality of channelinformation of the complex type in the above-described manner andmultiplying the information of the complex type of the multichannel by aspreading code sequence.

It is still another object of the present invention to provide anorthogonal complex spreading method for a multichannel and an apparatusthereof which is capable of decreasing the probability that the powerbecomes a zero state by preventing the FIR filter input state fromexceeding ±90° in an earlier sample state, increasing the powerefficiency, decreasing the consumption of a bias power for a back-off ofthe power amplifier and saving the power of a battery.

It is still another object of the present invention to provide anorthogonal complex spreading method for a multichannel and an apparatusthereof which is capable of implementing a POCQPSK (PermutatedOrthogonal Complex QPSK) which is another modulation method and has apower efficiency similar with the OCQPSK (Orthogonal Complex QPSK).

In order to achieve the above objects, there is provided an orthogonalcomplex spreading method for a multichannel which includes the steps ofcomplex-summing α_(n1)W_(M,n1)X_(n1) which is obtained by multiplying anorthogonal Hadamard sequence W_(M,n1) by a first data X_(n1) of a n-thblock and α_(n2)W_(M,n2)X_(n2) which is obtained by multiplying anorthogonal Hadamard sequence W_(M,n2) by a second data X_(n2) of a n-thblock; complex-multiplying α_(n1)W_(M,n1)X_(n1)+jα_(n2)W_(M,n2)X_(n2)which is summed in the complex type and W_(M,n3)+jW_(M,n4) of thecomplex type using a complex multiplier and outputting as an in-phaseinformation and quadrature-phase information; and summing only in-phaseinformation outputted from a plurality of blocks and onlyquadrature-phase information outputted therefrom and spreading the sameusing a spreading code.

In order to achieve the above objects, there is provided an orthogonalcomplex spreading apparatus according to a first embodiment of thepresent invention which includes a plurality of complex multiplicationblocks for distributing the data of the multichannel andcomplex-multiplying α_(n1)W_(M,n1)X_(n1)+jα_(n2)W_(M,n2)X_(n2) in whichα_(n1)W_(M,n1)X_(n1) which is obtained by multiplying the orthogonalHadamard sequence W_(M,n1) with the first data X_(n1) of the n-th blockand the gain α_(n1) and α_(n2)W_(M,n2)X_(n2) which is obtained bymultiplying the orthogonal Hadamard sequence W_(M,n2) with the seconddata X_(n2) of the n-th block and the gain α_(n2) and W_(M,n3)+W_(M,n4)using the complex multiplier; a summing unit for summing only thein-phase information outputted from each block of the plurality of thecomplex multiplication blocks and summing only the quadrature-phaseinformation; and a spreading unit for multiplying the in-phaseinformation and the quadrature-phase information summed by the summingunit with the spreading code and outputting an I channel and a Qchannel.

In order to achieve the above objects, there is provided an orthogonalcomplex spreading apparatus according to a second embodiment of thepresent invention which includes first and second Hadamard sequencemultipliers for allocating the multichannel to a predetermined number ofchannels, splitting the same into two groups and outputtingα_(n1)W_(M,n1)X_(n1) which is obtained by multiplying the data X_(n1) ofeach channel by the gain α_(n1) and the orthogonal Hadamard sequenceW_(M,n1);

-   -   a first adder for outputting

$\sum\limits_{n = 1}^{K}\;\left( {\alpha_{n\; 1}W_{M,{n\; 1}}X_{n\; 1}} \right)$

-   -    which is obtained by summing the output signals from the first        Hadamard sequence multiplier;    -   a second adder for outputting

$\sum\limits_{n = 1}^{K}\;\left( {\alpha_{n\; 2}W_{M,{n\; 2}}X_{n\; 2}} \right)$

-   -    which is obtained by summing the output signals from the second        Hadamard sequence multiplier, a complex multiplier for receiving        the output signal from the first adder and the output signal        from the second adder in the complex form of

$\sum\limits_{n = 1}^{K}\;\left( {{\alpha_{n\; 1}W_{M,{n\; 1}}X_{n\; 1}} + {{j\alpha}_{n\; 2}W_{M,{n\; 2}}X_{n\; 2}}} \right)$

-   -    and complex-multiplying W_(M,I)+jPW_(M,Q) which n=1 consist of        the orthogonal Hadamard code W_(M,I), and the permutated        orthogonal Hadamard code PW_(M,Q) that W_(M,Q) and a        predetermined sequence P are complex-multiplied; a spreading        unit for multiplying the output signal from the complex        multiplier by the spreading code; a filter for filtering the        output signal from the spreading unit; and a modulator for        multiplying and modulating the modulation carrier wave, summing        the in-phase signal and the quadrature-phase signal and        outputting a modulation signal of the real number.

Additional advantages, objects and other features of the invention willbe set forth in part in the description which follows and in part willbecome apparent to those having ordinary skill in the art uponexamination of the following or may be learned from practice of theinvention. The objects and advantages of the invention may be realizedand attained as particularly pointed out in the appended claims.

BRIEF DESCRIPTION OF THE DRAWINGS

The present invention will become more fully understood from thedetailed description given hereinbelow and the accompanying drawingswhich are given by way of illustration only, and thus are not limitativeof the present invention, and wherein;

FIG. 1 is a block diagram illustrating a conventional multichannelcomplex spreading method of a CDMA (Code Division Multiple Access) ONEmethod;

FIG. 2A is a view illustrating a constellation plot of a conventionalCDMA ONE method;

FIG. 2B is a view illustrating a maximum open point after the actualshaping filter of FIG. 2A;

FIG. 3A is a view illustrating a constellation plot of a conventionalETRI version 1.0 method;

FIG. 3B is a view illustrating a maximum open point after the actualpulse shaping filter of FIG. 3A;

FIG. 4 is a block diagram illustrating a multichannel orthogonal complexspreading apparatus according to the present invention;

FIG. 5A is a circuit diagram illustrating the complex multiplexor ofFIG. 4;

FIG. 5B is a circuit diagram illustrating the summing unit and spreadingunit of FIG. 4;

FIG. 5C is a circuit diagram illustrating another embodiment of thespreading unit of FIG. 4;

FIG. 5D is a circuit diagram illustrating of the filter and modulator ofFIG. 4;

FIG. 6A is a view illustrating a constellation plot of an OCQPSKaccording to the present invention;

FIG. 6B is a view illustrating a maximum open point after the actualpulse shaping filter of FIG. 6A;

FIG. 7 is a view illustrating a power peak occurrence statisticaldistribution characteristic with respect to an average power between theconventional art and the present invention;

FIG. 8 is a view illustrating an orthogonal Hadamard sequence accordingto the present invention;

FIG. 9 is a circuit diagram illustrating a multichannel permutatedorthogonal complex spreading apparatus according to the presentinvention;

FIG. 10 is a circuit diagram illustrating the complex multiplieraccording to the present invention;

FIG. 11 is a circuit diagram illustrating a multichannel permutatedorthogonal complex spreading apparatus for a voice service according tothe present invention;

FIG. 12 is a circuit diagram illustrating a multichannel permutatedorthogonal complex spreading apparatus having a high quality voiceservice and a low transmission rate according to the present invention;

FIG. 13A is a circuit diagram illustrating a multichannel permutatedorthogonal complex spreading apparatus for a QPSK having a hightransmission rate according to the present invention;

FIG. 13B is a circuit diagram illustrating a multichannel permutatedorthogonal complex spreading apparatus for a data having a hightransmission rate according to the present invention;

FIG. 14A is a circuit diagram illustrating a multichannel permutatedorthogonal complex spreading apparatus for a multimedia service having aQPSK data according to the present invention;

FIG. 14B is a circuit diagram illustrating a multichannel permutatedorthogonal complex spreading apparatus for a multimedia serviceaccording to the present invention;

FIG. 15A is a phase trajectory view of an OCQPSK according to thepresent invention;

FIG. 15B is a phase trajectory view of a POCQPSK according to thepresent invention; and

FIG. 15C is a phase trajectory view of a complex spreading methodaccording to the present invention.

DETAILED DESCRIPTION OF THE INVENTION

The complex summing unit and complex multiplier according to the presentinvention will be explained with reference to the accompanying drawings.In the present invention, two complexes (a+jb) and (c+jd) are used,where a, b, c and d represent predetermined real numbers.

A complex summing unit outputs (a+c)+j(b+d), and a complex multiplieroutputs ((a×c)−(b×d))+j((b×c)+(a×d)). Here, a spreading code sequence isdefined as SC, an information data is defined as X_(n1), and X_(n2), again constant is defined as α_(n1) and α_(n2), and an orthogonalHadamard sequence is defined as W_(M,n1), W_(M,n2), W_(M,n3), W_(M,n4),W_(M,I), W_(M,Q), where M represents a M×M Hadamard matrix, and n1, n2,n3 and n4 represents index of a predetermined vector of the Hadamardmatrix. For example, n3 represents a Hadamard vector which is a thirdvector value written into the n-th block like the n-th block 100n ofFIG. 4. The Hadamard M represents a Hadamard matrix. For example, if thematrix W has values of 1 and −1, in the W_(T)×W, the main diagonal termsare M, and the remaining products are zero. Here, T represents atranspose.

The data X_(n1), X_(n2), W_(M,n1), W_(M,n2), W_(M,n3), W_(M,n4),W_(M,I), and W_(M,Q), and SC are combined data consisting of +1 or −1,and any and α_(n2) represent real number.

FIG. 4 is a block diagram illustrating a multichannel orthogonal complexspreading apparatus according to the present invention.

As shown therein, there is provided a plurality of complex multipliers100 through 100n in which a data of a predetermined channel ismultiplied by a gain and orthogonal Hadamard sequence, and a data ofanother channel is multiplied by the orthogonal Hadamard sequence forthereby complex-summing two channel data, the orthogonal Hadamardsequence of the complex type is multiplied by the complex-summed data,and the data of other two channels are complex-multiplied in the samemanner described above. A summing unit 200 sums and outputs the outputsignals from the complex multipliers 100 through 100n. A spreading unit300 multiplies the output signal from the summing unit 200 with apredetermined spreading code SC for thereby spreading the signal. Apulse shaping filter 400 filters the data spread by the spreading unit300. A modulation wave multiplier 500 multiplies the output signal fromthe filter 400 with a modulation carrier wave and outputs the modulateddata through an antenna.

As shown in FIG. 4, the first complex multiplier 100 complex-sumsα₁₁W_(M,11)X₁₁ which is obtained by multiplying the orthogonal Hadamardsequence W_(M,11) with the data X₁₁ of one channel and the gain α₁₁ andα₁₂W_(M,12)X₁₂ which is obtained by multiplying the orthogonal Hadamardsequence W_(M,12) with the data X₁₂ of another channel and the gain α₁₂,and complex-multiplies α₁₁W_(M,11)X₁₁+jα₁₂W_(M,12)X₁₂ and thecomplex-type orthogonal sequence W_(M,13)X₁₁+jW_(M,14) using the complexmultiplier 111.

In addition, the n-th complex multiplier 100n complex-sumsα_(n1)W_(M,n1)X_(n1) which is obtained by multiplying the orthogonalHadamard sequence W_(M,n1) with the data X_(n1) of another channel andthe gain α_(n1) and α_(n2)W_(M,n2)X_(n2) which is obtained bymultiplying the orthogonal Hadamard sequence W_(M,n2) with the dataX_(n2) of another channel and the gain α_(n2), and complex-multipliesα_(n1)W_(M,n1)X_(n1)+jα_(n2)W_(M,n2)X_(n2) and the complex-typeorthogonal sequence W_(M,n3)X₁₁+jW_(M,n4) using the complex multiplier100n.

The complex multiplication data outputted from the n-number of thecomplex multipliers are summed by the summing unit 200, and thespreading code SC is multiplied and spread it by the spreading unit 300.The thusly spread data are filtered by the pulse shaping filter 600, andthe modulation carried e^(j2πfct) is multiplied by the multiplier 700,and then the function Re{*} is processed, and the real data s(t) isoutputted through the antenna. Here, Re{*} represents that apredetermined complex is processed to a real value through the Re{*}function.

The above-described function will be explained as follows:

$\left( {\sum\limits_{n = 1}^{K}\;\left( {\left( {{\alpha_{n\; 1}W_{M,{n\; 1}}X_{n\; 1}} + {{j\alpha}_{n\; 2}W_{M,{n\; 2}}X_{n\; 2}}} \right) \otimes \left( {W_{M,{n\; 3}} + \left( {jW} \right)_{M,{n\; 4}}} \right)} \right)} \right) \otimes {SC}$where K represents a predetermined integer greater than or equal to 1, nrepresents an integer greater than or equal to 1 and less than K and isidentical with each channel number of the multichannel.

Each of the complex multipliers 110 through 100n is identicallyconfigured so that two different channel data are complex-multiplied.

As shown in FIG. 5A, one complex multiplier includes a first multiplier101 for multiplying the data X₁₁ by the orthogonal Hadamard sequenceW_(M,11) a second multiplier for multiplying the input signal from thefirst multiplier by the gain α₁₁, a third multiplier 103 for multiplyingthe data X₁₂ of the other channel by another orthogonal Hadamardsequence W_(M,12), a fourth multiplier 104 for multiplying the outputsignal from the third multiplier 103 by the gain α₁₂, fifth and sixthmultipliers 105 and 106 for multiplying the as output signalsα₁₁W_(M,11)X₁₁ from the second multiplier 102 and the output signalsα₁₁W_(M,12)X₁₂ from the fourth multiplier 102 by the orthogonal Hadamardsequence W_(M,13), respectively, seventh and eighth multipliers 107 and108 for multiplying the output signal α₁₁W_(M,11)X₁₁ from the secondmultiplier 102 and the output signal α₁₂W_(M,12)X₁₂ from the fourthmultiplier 102 by the orthogonal Hadamard sequence W_(M,14),sequentially, a first adder 109 for summing the output signal (+ac) fromthe fifth multiplier 105 and the output signal (−bd) from the eighthmultiplier 108 and outputting in-phase information (ac−bd), and a secondadder 110 for summing the output signal (bc) from the sixth multiplier106 and the output signal (ad) from the seventh multiplier 107 andoutputting the quadrature-phase information (bc+ad).

Therefore, the first and-second multipliers 101 and 102 multiply thedata X₁₁ by the orthogonal Hadamard sequence W_(M,11) and the gain α₁₁for thereby obtaining α₁₁W_(M,11)X₁₁ (=a). In addition, the third andfourth multipliers 103 and 104 multiply the orthogonal Hadamard sequenceW_(M,12) and the gain α₁₂ for thereby obtaining α₁₂W_(M,12)X₁₂ (=b). Thefifth and sixth multipliers 105 and 106 multiply α₁₁W_(M,11)X₁₁ (=a) andα₁₂W_(M,12)X₁₂ (=b) by the orthogonal Hadamard sequence W_(M,13) (=c),respectively, for thereby obtaining α₁₁W_(M,11)X₁₁W_(M,13) (=ac) andα₁₂W_(M,12)X₁₂W_(M,13) (=bc), and the fifth and sixth multipliers 105and 106 multiply α₁₁W_(M,11)X₁₁ (=a) and α₁₂W_(M,12)X₁₂ (=b) by theorthogonal Hadamard sequence W_(M,14) (=d) for thereby obtainingα₁₁W_(M,11)X₁₁W_(M,14) (=ad) and α₁₂W_(M,12)X₁₂W_(M,14) (=bd). Inaddition, the first adder 109 computes(α₁₁W_(M,11)X₁₁W_(M,13))−(α₁₂W_(M,12)X₁₂W_(M,14)) (=ac−bd), namely,α₁₂W_(M,12)X₁₂W_(M,14) is subtracted from α₁₁W_(M,11)X₁₁W_(M,13). Inaddition, the second adder 110 computes(α₁₁W_(M,11)X₁₁W_(M,14))+(α₁₂W_(M,12)X₁₂W_(M,13)) (ad+bc), namely,α₁₁W_(M,11)X₁₁W_(M,14) (=ad) is added with α₁₂W_(M,12)X₁₂W_(M,13) (=bc).

FIG. 4 illustrates the first complex multiplier 100 which is configuredidentically with the n-th complex multiplier 100n. Assuming thatα₁₁W_(M,11)X₁₁ is “a”, α₁₂W_(M,12)X₁₂ is “b”, the orthogonal Hadamardsequence W_(M,13) is “c”, and the orthogonal Hadamard sequence W_(M,14)is “d”, the expression “(a+jb) (c+jd)=ac−bd+j (bc+ad)” is obtained.Therefore, the signal outputted from the first complex multiplier 100becomes the in-phase information “ac−bd” and the quadrature-phaseinformation “bc+ad”.

In addition, FIG. 5B is a circuit diagram illustrating the summing unitand spreading unit of FIG. 4, and FIG. 5C is a circuit diagramillustrating another embodiment of the spreading unit of FIG. 4.

As shown therein, the summing unit 200 includes a first summing unit 210for summing the in-phase information A₁(=(ac−bd), . . . , An outputtedfrom a plurality of complex multipliers, and a second summing unit 220for summing the quadrature-phase information B₁(=bc+ad) outputted fromthe complex multipliers.

The spreading unit 300 includes first and second multipliers 301 and 302for multiplying the output signals from the first adder 210 and thesecond adder 220 of the summing unit 200 by the spreading sequence SC,respectively. Namely, the signals are spread to the in-phase signal (Ichannel signal) and the quadrature-phase signal (Q channel signal) usingone spreading code SC.

In addition, as shown in FIG. 5C, the spreading unit 300 includes firstand second multipliers 310 and 320 for multiplying the output signalsfrom the first and second adders 210 and 220 of the summing unit 200 bythe spreading sequence SC1, third and fourth multipliers 330 and 340 formultiplying the output signals from the first and second adders 210 and220 by a spreading sequence SC2, respectively, a first adder 350 forsumming the output signal (+) from the first multiplier 310 and theoutput signal (−) from the third multiplier 330 and outputting an Ichannel signal, and a second summing unit 360 for summing the outputsignal (+) from the second multiplier 320 and the output signal (+) fromthe fourth multiplier 340 and outputting a Q channel signal.

Namely, in the summing unit 200, the in-phase information and thequadrature-phase information of the n-number of the complex multipliersare summed by the first and second summing units 210 and 220. In thespreading unit 300, the in-phase information summing value (g) and thequadrature phase information summing value (h) from the summing unit 200are multiplied by the first spreading code SC1 (1) by the first andsecond multipliers 310 and 320 for thereby obtaining gl and hl, and thein-phase information summing value (g) and the quadrature phaseinformation summing value (h) from the summing unit 200 are multipliedby the second spreading code SC2(m) by the third and fourth multipliers330 and 340 for thereby obtaining gm and hm, and the first adder 350computes gl−hm in which hm is subtracted from gl, and the second adder360 computes hl+gm in which hl is added by gm.

As shown in FIG. 5D, the filter 400 includes first and second pulseshaping filters 410 and 420 for filtering the I channel signal which isthe in-phase information shown in FIGS. 5B and 5C and the channel signalwhich is the quadrature phase information signal. The modulation unit500 includes first and second multipliers 510 and 520 for multiplyingthe output signals from the first and second pulse shaping filters 410and 420 by cos(2πf_(c)t) and sin (2πf_(c)t), and an adder 530 forsumming the output signals from the multipliers 510 and 520 andoutputting a modulation data S(t).

Here, the orthogonal Hadamard sequences may be used as a Walsh code orother orthogonal code.

For example, from now on, the case that the orthogonal Hadamard sequenceis used for the 8×8 Hadamard matrix shown in FIG. 8 will be explained.

FIG. 8 illustrates an example of the Hadamard (or Walsh) code. Namely,the case that the sequence vector of a k-th column or row is set toW_(k-1) based on the 8×8 Hadamard matrix is shown therein. In this case,if k is 1, W_(k-1) represents W₀ of the column or row, and if k is 5,W_(k-1) represents W₄ of the column or row.

Therefore, in order to enhance the efficiency of the present invention,the orthogonal Hadamard sequence which multiplies each channel data isdetermined as follows.

In the M×M Hadamard matrix, the sequence vector of the k-th column orrow is set to W_(k-1), and W_(M,n1)=W₀, W_(M,n2)=W_(2p) (where prepresents a predetermined number of (M/2)−1), and W_(M,n3)=W_(2n-2),W_(M,n4)=W_(2n-1) (where n represents the number of n-th blocks), andα_(n1)W₀X_(n1)+jα_(n2)W_(2p)X_(n2) and W_(2n-2)+jW_(2n-1). The case thatonly first complex multiplier is used in the embodiment of FIG. 4,namely, the data of two channels are complex-multiplied will beexplained. In the M×M (M=8) Hadamard matrix, if the k-th column or rowsequence vector is set to W_(k-1), it is possible to determineW_(M,11)=W₀, W_(M,12)=W₂, or W_(M,12)=W₄, and W_(M,13)=W₀, W_(M,14)=W₁.In addition, it is possible to complex-multiply α₁₁W₀X₁₁+jα₁₂W₂X₁₂ orα₁₁W₀X₁₁+jα₁₂W₄X₁₂ and W₀+jW₁.

In the case that two complex multipliers shown in FIG. 4 are used, thesecond complex multiplier determines W_(M,21)=W₀, W_(M,22)=W₄, andW_(M,23)=W₂, and W_(M,24)=W₃, so that it is possible to complex-multiplyα₂₁W₀X₂₁+jα₂₂W₄X₂₂ and W₂+jW₃.

In addition, as shown in FIG. 5, when the spreading is implemented byusing the spreading code SC, one spreading code may be used, and asshown in FIG. 5C, two spreading codes SC1 and SC2 may be used forthereby implementing the spreading operation.

In order to achieve the objects of the present invention, the orthogonalHadamard sequence directed to multiplying each channel data may bedetermined as follows.

The combined orthogonal Hadamard sequence may be used instead of theorthogonal Hadamard sequence for removing a predetermined phasedependency based on the interference generated in the multiple path typeof self-signal and the interference generated by other users.

For example, in the case of two channels, when the sequence vector ofthe k-th column or row is set to W_(k-1) in the M×M (M=8) Hadamardmatrix, and the sequence vector of the m-th column or row is set toW_(m), the first M/2 or the last M/2 is obtained based on the vectorW_(k-1) and the last M/2 or the first M/2 is obtained based on W_(m-1),so that the combined orthogonal Hadamard vector is set to W_(k-1/m-1),and W_(M,11)=W₀, W_(M,12)=W_(4//1), W_(M/I)=W₀, W_(M,Q=W1/4) aredetermined, so that it is possible to complex-multiplyα₁₁W₀X₁₁+jα₁₂W_(4//1)X₁₁ and W₀+jPW_(1//4).

In the case of three channels, the sequence vector of the k-th column orrow is set to W_(k-1) based on the M×M (M=8) Hadamard matrix, and thesequence vector of the m-th column or row is set to W_(M), so that thefirst M/2 or the last M/2 is obtained from the vector W_(k-1), and thelast M/2 or the first M/2 is obtained from W_(m-1), and the combinedorthogonal Hadamard vector is set to W_(k-1/m-1), and the summed valueof α₁₁W₀X₁₁+jα₁₂W_(4//1)X₁₂ and α₂₁W₂X₂₁ and W₀+jPW_(1//4) are complexmultiplied based on W_(M,11)=W₀, W_(M,12)=W_(4//1), W_(M,21)=W₁, andW_(M,I)=W₀, W_(M,Q)=W_(1//4).

In addition, in the case of two channels, when the sequence vector ofthe k-th column or row of the M×M (M=8) Hadamard vector matrix is set toW_(k-1), and the sequence vector of the m-th column or row is set toW_(m), the first M/2 or the last M/2 is obtained from the vectorW_(k-1), and the last M/2 or the first M/2 is obtained from W_(m-1), sothat the combined orthogonal Hadamard vector is set to W_(-1//m-1), andthe summed value of α₁₁W₀X₁₁+jα₁₂W_(2//1)X₁₂ and W₀+jPW_(1//2) arecomplex-multiplied based on W_(M,11)=W₀, W_(M,12)=W_(2//1), andW_(M,I)=W₀, W_(M,Q)=W_(1//2).

In addition, in the case of three channels, when the sequence vector ofthe k-th column or row of the M×M (M=8) Hadamard vector matrix is set toW_(k-1), and the sequence vector of the m-th column or row is set toW_(m), the first M/2 or the last M/2 is obtained from the vectorW_(k-1), and the last M/2 or the first M/2 is obtained from W_(m-1), sothat the combined orthogonal Hadamard vector is set to W_(k-1/m-1), andthe summed value of α₁₁W₀X₁₁+jα₁₂W_(2//1)X₁₂ and α₂₁W₄X₂₁ andW₀+jPW_(1//2) are complex-multiplied based on W_(M,11)=W₀,W_(M,12)=W_(2//1), W_(M,21)=W₄, and W_(M,I=W0), W_(M,Q)=W_(1//2).

Here, so far the cases of two channels and three channels wereexplained. The cases of two channels and three channels may beselectively used in accordance with the difference of the impulseresponse characteristic difference of the pulse shaping bandpass filter.

FIG. 6A is a view illustrating a constellation plot of the OCQPSKaccording to the present invention, FIG. 6B is a view illustrating amaximum eye-opening point after the actual pulse shaping filter of FIG.6A, and FIG. 7 is a view illustrating a power peak occurrencestatistical distribution characteristic with respect to an average powerbetween the OCQPSK according to the present invention and theconventional CDMA ONE and version ETRI 1.0. As shown therein, theembodiment of FIG. 6A is similar with that of FIG. 2A. However, there isa difference in the point of the maximum eye-opening point after theactual pulse shaping filter. Namely, in FIG. 6B, the range of the upperand lower information (Q channel) and the left and right information (Ichannel) are fully satisfied. This causes the difference of thestatistical distribution of the peak power-to-average power.

FIG. 7 illustrates the peak power-to-average power ratio obtained basedon the result of the actual simulation between the present invention andthe conventional art.

In order to provide the identical conditions, the power level of thecontrol or signal channel is controlled to be the same as the powerlevel of the communication channel (Fundamental channel, supplementalchannel or the In-phase channel and the Quadrature channel), and thepower level of the pilot channel is controlled to be lower than thepower level of the communication channel by 4 dB. In the above-describedstate, the statistical distributions of the peak power-to-average powerare compared.

In the case of OCQPSK according to the present invention, the comparisonis implemented using the first complex multiplier 100 and the n-thcomplex multiplier 100n shown in FIG. 4. The first block 100 isimplemented based on W_(M,11)=W₀, W_(M,12)=W₄, W_(M,13)=W₀, andW_(M,14)=W₁, and the n-th block 100n is implemented based onW_(M,n1)=W₀, W_(M,n2)=W₄, W_(M,n3)=W₂, and W_(M,n4)=W₃. In addition, theSCI is used as the SC1 for the spreading code. In this case, the SC2 isnot used.

In the case of OCQPSK, the probability that the instantaneous powerexceeds the average power value (0 dB) by 4 dB is 0.03%, and in the caseof CDMA ONE, the same is 0.9%, and in the case of the ETRI version 1.0,the same is 4%. Therefore, in the present invention, the system usingthe CDMA technique has very excellent characteristic in the peak toaverage power ratio sense, and the method according to the presentinvention is a new modulation method which eliminates the cross talkproblem.

FIG. 9 illustrates a permutated orthogonal complex spreading modulation(POCQPSK) according to the present invention.

As shown therein, one or a plurality of channels are combined andcomplex-multiplied by the permutated orthogonal Hadamard code and thenare spread by the spreading code.

As shown therein, there are provided first and second Hadamard sequencemultipliers 600 and 700 for allocating the multichannel to apredetermined number of channels, splitting the same into two groups andoutputting α_(n1)W_(M,n1)X_(n1) which is obtained by multiplying thedata X_(n1) of each channel by the gain α_(n1) and the orthogonalHadamard sequence W_(M,n1), a first adder 810 for outputting

$\sum\limits_{n = 1}^{K}\;\left( {\alpha_{n\; 1}W_{M,{n\; 1}}X_{n\; 1}} \right)$which is obtained by summing the output signals from the first Hadamardsequence multiplier 600, a second adder 820 for outputting

$\sum\limits_{n = 1}^{K}\;\left( {\alpha_{n\; 2}W_{M,{n\; 2}}X_{n\; 2}} \right)$which is obtained by summing the output signals from the second Hadamardsequence multiplier 700, a complex multiplier 900 for receiving theoutput signal from the first adder 810 and the output signal from thesecond adder 820 in the complex form of

$\sum\limits_{n = 1}^{K}\;\left( {{\alpha_{n\; 1}W_{M,{n\; 1}}X_{n\; 1}} + {{j\alpha}_{n\; 2}W_{M,{n\; 2}}X_{n\; 2}}} \right)$and complex-multiplying W_(M,I)+jPW_(M,Q) which consist of theorthogonal Hadamard code W_(M,I), and the permutated orthogonal Hadamardcode PW_(M,Q) that W_(M,Q) and a predetermined sequence P arecomplex-multiplied, a spreading unit 300 for multiplying the outputsignal from the complex multiplier 900 by the spreading code, a filter400 for filtering the output signal from the spreading unit 300, and amodulator 500 for multiplying and modulating the modulation carrierwave, summing the in-phase signal and the quadrature phase signal andoutputting a modulation signal of the real number.

Here, the construction of the spreading unit 300, the filter 400 and themodulator 500 is the same as the embodiment of FIG. 4 except for thefollowing construction. Namely, comparing to the embodiment of FIG. 4,in the construction of FIG. 9, the multiplication of the complex typeorthogonal Hadamard sequence performed by the complex multipliers 100through 100n are separated and connected in the rear portion of thesumming unit, and the channel-wise multiplication by the complex typeorthogonal Harmard sequence is not implemented. Namely, the two groupsummed signal is multiplied by the complex type orthogonal Hadamardsequence.

The first orthogonal Hadamard sequence multiplier 600 outputs

$\sum\limits_{n = 1}^{K}\;\left( {\alpha_{n\; 1}W_{M,{n\; 1}}X_{n\; 1}} \right)$which is summed by the first adder 810 by summing α₁₁W_(M,11)X₁₁ whichis obtained by the first adder 810 by multiplying the orthogonalHadamard sequence W_(M,11) by the first data X₁₁ of the first block andthe gain α₁₁, respectively, α₂₁W_(M,21)X₂₁ which is obtained bymultiplying the orthogonal Hadamard sequence W_(M,21) by the second dataX₂₁ of the first block and the gain α₂₁, respectively, andα_(n1)W_(M,n1)X_(n1) which is obtained by multiplying the orthogonalHadamard sequence W_(M,n1) by the n-th data X_(n1) of the first blockand the gain α_(n1).

The second orthogonal Hadamard sequence multiplier 700 outputs

$\sum\limits_{n = 1}^{K}\;\left( {\alpha_{n\; 2}W_{M,{n\; 2}}X_{n\; 2}} \right)$which is summed by the second adder 820 by summing α₁₂W_(M,12)X₁₂ whichis obtained by multiplying the orthogonal Hadamard sequence W_(M,12) bythe first data X₁₂ of the second block and the gain α₁₂, respectively,α₂₂W_(M,22)X₂₂ which is obtained by multiplying the orthogonal Hadamardsequence W_(M,22) by the second data X₂₂ of the second block and thegain α₂₂, respectively, and α_(n2)W_(M,n2)X_(n2) which is obtained bymultiplying the orthogonal Hadamard sequence W_(M,n2) by the n-th dataX_(n2) of the second block and the gain α_(n2). Here, the blockrepresents one group split into 1 group.

The signal outputted from the first adder 810 forms an in-phase data,and the signal outputted from the second adder 820 forms an quadraturephase data and outputs

$\sum\limits_{n = 1}^{K}\;{\left( {{\alpha_{n\; 1}W_{M,{n\; 1}}X_{n\; 1}} + {{j\alpha}_{n\; 2}W_{M,{n\; 2}}X_{n\; 2}}} \right).}$In addition, the complex multiplier 900 multiplies the complex outputsignals from the first and second adders 810 and 820 by a complex typesignal that is comprised of an orthogonal Harmard code W_(M,I) andPW_(M,Q) which results from the multiplication of the orthogonalHardmard code W_(M,Q) by the sequence P and outputs an in-phase signaland a quadrature phase signal. Namely, the complex output signals fromthe first and second adders 810 and 820 are complex-multiplied by thecomplex type signals of W_(M,I)+jPW_(M,Q) by the complex multiplier.

The spreading unit 300 multiplies the output signal from the complexmultiplier 900 by the spreading code SCI and spreads the same. Thethusly spread signals are filtered by the pulse shaping filters 410 and420. The modulation carrier waves of cos(2πf_(c)t) and sin(2πf_(c)t) aresummed by the modulation multipliers 510 and 520 and then modulated forthereby outputting s(t).

Namely, the following equation is obtained.

$\left( {\sum\limits_{n = 1}^{K}\;\left( {{\alpha_{n\; 1}W_{M,{n\; 1}}X_{n\; 1}} + {{j\alpha}_{n\; 2}W_{M,{n\; 2}}X_{n\; 2}}} \right)} \right) \otimes \left( {W_{M,I} + \left( {j{PW}} \right)_{M,Q}} \right) \otimes {{SCI}.}$where K represents an integer greater than or equal to 1.

FIG. 10 illustrates an embodiment that two channel data arecomplex-multiplied. A channel data X₁₁ is allocated to the firstorthogonal Hadamard sequence multiplier 600 and another channel data X₁₂is allocated to the second orthogonal Hadamard sequence multiplier 700.

Here, the orthogonal Hadamard sequence multiplier includes a firstmultiplier 610 for multiplying the first data X₁₁ by the gain α₁₁, asecond multiplier 611 for multiplying the output signal from the firstmultiplier 610 by the orthogonal Hadamard sequence W_(M,11), a thirdmultiplier 710 for multiplying the second data X₁₂ by the gain α₁₂, anda fourth multiplier 711 for multiplying the output signal from the thirdmultiplier 710 by the orthogonal Hadamard sequence W_(M,12). At thistime, since one channel is allocated to one group, the summing unit isnot used.

The complex multiplier 900 includes fifth and sixth multipliers 901 and902 for multiplying the output signal α₁₁W_(M,11)X₁₁ from the secondmultiplier 611 and the output signal α₁₂W_(M,12)X₁₂ from the fourthmultiplier 711 by the orthogonal Hadamard sequence seventh and eighthmultipliers 903 and 904 for multiplying the output signal α₁₁W_(M,11)X₁₁from the second multiplier 611 and the output signal α₁₂W_(M,12)X₁₂ fromthe fourth multiplier 711 by the permutated orthogonal Hadamard sequencePW_(M,Q), a first adder 905 for summing the output signal (+ac) from thefifth multiplier 901 and the output signal (−bd) from the seventhmultiplier 903 and outputting an in-phase information (ac−bd), and asecond adder 906 for summing the output signal (bc) from the sixthmultiplier 902 and the output signal (ad) from the eighth multiplier 904and outputting an quadrature phase information (bc+ad).

Therefore, the first and second multipliers 610 and 611 multiply thedata X₁₁ by the orthogonal Hadamard sequence W_(M,11) and the gain α₁₁for thereby obtaining α₁₁W_(M,11)X₁₁ (=a). In addition, the third andfourth multipliers 710 and 711 multiply the data X₁₂ by the orthogonalHadamard sequence W_(M,12) and the gain α₁₂ for thereby obtainingα₁₂W_(M,12)X₁₂ (=b). The fifth and sixth multipliers 901 and 902multiply α₁₁W_(M,11)X₁₁ (=a) and α₁₂W_(M,12)X₁₂ (=b) by the orthogonalHadamard sequence W_(M,I) (=c) for thereby obtainingα₁₁W_(M,11)X₁₁W_(M,I) (=ac) and α₁₂W_(M,12)X₁₂W_(M,I) (=bc).

The seventh and eighth multipliers 903 and 904 multiply α₁₁W_(M,11)X₁₁(=a) and α₁₂W_(M,12)X₁₂ (=b) by the permutated orthogonal Hadamardsequence PW_(M,Q) for thereby obtaining α₁₁W_(M,11)X₁₁PW_(M,Q) (=ad) andα₁₂W_(M,12)X₁₂PW_(M,Q) (=bd).

In addition, the first adder 905 obtains(α₁₁W_(M,11)X₁₁W_(M,I))−(α₁₂W_(M,12)X₁₂PW_(M,Q)) (=ac−bd), namely,α₁₂W_(M,12)X_(12PWM,Q)(bd) is subtracted from α₁₁W_(M,11)X₁₁W_(M,I)(=ac), and the second adder 906 obtains(α₁₁W_(M,11)X₁₁PW_(M,Q))+(α₁₂W_(M,12)X₁₂W_(M,I)) (ad+bc), namely,(α₁₁W_(M,11)X₁₁PW_(M,Q)) (=ad) is summed by (α₁₂W_(M,12)X₁₂W_(M,I))(bc).

FIG. 10 illustrates the complex multiplier 900 shown in FIG. 9. Assumingthat α₁₁W_(M,11)X₁₁ is “a”, α₁₂W_(M12)X₁₂ is “b”, the orthogonalHadamard sequence W_(M,I) is “c”, and the permutated orthogonal Hadamardsequence PW_(M,Q) is “d”, since (a+jb) (c+jd)=ac−bd+jc (bc+ad), thesignal from the complex multiplier 900 becomes the in-phase informationac−bd and the quadrature phase information bc+ad.

The in-phase data and the quadrature phase data are spread by thespreading unit 300 based on the spreading code (for example, PN code).In addition, the I channel signal which is the in-phase information andthe Q channel signal which is the quadrature phase information signalare filtered by the first and second pulse shaping filters 410 and 420.The first and second multipliers 510 and 520 multiply the output signalsfrom the first and second pulse shaping filters 410 and 420 bycos(2πf_(c)t) and sin(2πf_(c)t). The output signals from the multipliers510 and 520 are summed and modulated by the adder 530 which outputsS(t).

In the embodiment as shown in FIG. 9, identically to the embodiment asshown in FIG. 4, for the orthogonal Hadamard sequence, the Walsh code orother orthogonal code may be used. In addition, in the orthogonalHadamard sequence of each channel, the sequence vector of the k-thcolumn or row is set to W_(k-1) in the M×M Hadamard matrix. Therefore,α_(n1)W₀X_(n1)+jα_(n2)W_(2p)X_(n2) and W₀+jPW₁ are complex-multipliedbased on W_(M,n1)=W₀, W_(M,n2)=W_(2p) (where p represents apredetermined number in a range from 0 to (M/2)−1.

The orthogonal Hadamard sequence is allocated to each channel based onthe above-described operation, and if there remain other channels whichare not allocated the orthogonal Hadamard sequence by theabove-described operation, and if there remain other channel which arenot allocated the orthogonal Hadamard sequence by the above-described isoperation, then any row or column vector from the Hamard matrix can beselected.

FIG. 11 illustrates an embodiment of the POCQPSK for the voice service.In this case, two channels, namely, the pilot channel and the data oftraffic channels are multiplied by the gain and orthogonal Hadamardsequence, and two channel signals are inputted into the complexmultiplier 900 in the complex type, and the orthogonal Hadamard sequenceof the complex type is multiplied by the complex multiplier 900.

FIG. 12 illustrates the construction of a data service having a goodquality voice service and low transmission rate. In this case, the pilotchannel and signaling channel are allocated to the first orthogonalHadamard sequence multiplier 700, and the traffic channel is allocatedto the second orthogonal Hadamard sequence multiplier 700.

FIG. 13A illustrates the construction for a data service of a hightransmission rate. As shown therein, the data transmitted at a rate of Rbps has the QPSK data type and are transmitted at R/2 bps through theserial to parallel converter. As shown in FIG. 13B, the system may beconstituted so that the input data (traffic 1 and traffic 2) have theidentical gains (α₃₁=α₁₂). Here, when the data having high transmissionrate are separated into two channels, the gain allocated to each channelshould be determined to the identical gain for thereby eliminating thephase dependency.

FIGS. 14A and 14B illustrate the construction of the multichannelservice. In this case, the data (traffic) having a high transmissionrate is converted into the QPSK data for R/2 bps through the serial toparallel converter and then is distributed to the first orthogonalHadamard sequence multiplier 600 and the second Hadamard sequencemultiplier 700, and three channels are allocated to the first orthogonalHadamard sequence multiplier 600 and two channels are allocated to thesecond orthogonal Hadamard sequence multiplier 700.

As shown in FIG. 14B, the serial to parallel converter is not used, andwhen the data (traffic) is separated into two channel data (Traffic 1)and (traffic 2) and then is inputted, the gain adapted to each channeladapts the identical gains (α31=α12).

FIG. 15A is a phase trajectory view of an OCQPSK according to thepresent invention, FIG. 15B is a phase trajectory view of a POCQPSKaccording to the present invention, and FIG. 15C is a phase trajectoryview of a complex spreading method according to PN complex spreadingmethod of the present invention.

As shown therein, when comparing the embodiments of FIGS. 15A, 15B and15C, the shapes of the trajectories and the zero points are different.In a view of the power efficiency there is also a difference. Thereforethe statistical distribution of the peak power-to-average power ratio isdifferent.

FIG. 7 illustrates a characteristic illustrating a statisticaldistribution of a peak power-to-average power ratio of the CDMA ONEmethod compared to the OCQPSK method and the POSQPSK.

In order to provide the identical condition, the power level of thesignal channel is controlled to be the same as the power level of thecommunication channel, and the power level of the pilot channel iscontrolled to be lower than the power level of the communication channelby 4 dB, and then the statistical distribution of the peakpower-to-average power ratio is compared.

In the case of the POCQPSK according to the present invention, in thefirst block 600 of FIG. 9, W_(M,11)=W₀, and W_(M,21)=W₂ are implemented,and in the second block 700, W_(M,12)=W₄, and W_(M,I)=W₀ and W_(M,Q)=W₁are implemented. For the value of P, the spreading code is used so thatconsecutive two sequences have the identical value.

For example, the probability that the instantaneous power exceeds theaverage power value (0 dB) by 4 dB is 0.1% based on POCQPSK, and thecomplex spreading method is 2%. Therefore, in view of the powerefficiency, the method adapting the CDMA technique according to thepresent invention is a new modulation method having excellentcharacteristic.

As described above, in the OCQPSK according to the present invention,the first data and the second data are multiplied by the gain andorthogonal code, and the resultant values are complex-summed, and thecomplex summed value is complex-multiplied by the complex typeorthogonal code. The method that the information of the multichannel ofthe identical structure is summed and then spread is used. Therefore,this method statistically reduces the peak power-to-average power ratioto the desired range.

In addition, in the POCQPSK according to the present invention, the dataof the first block and the data of the second block are multiplied bythe gain and the orthogonal code, respectively, and the permutatedorthogonal spreading code of the complex type is complex-multiplied andthen spread. Therefore, this method statistically reduces the peakpower-to-average power ratio to the desired range, and it is possible todecrease the phase dependency based in the multichannel interference andthe multiuser interference using the combined orthogonal Hadamardsequence.

Although the preferred embodiments of the present invention have beendisclosed for illustrative purposes, those skilled in the art willappreciate that various modifications, tat additions and substitutionsare possible, without departing from the scope and spirit of theinvention as recited in the accompanying claims.

What is claimed is:
 1. An orthogonal complex spreading method formultiple channels, comprising the steps of: complex-summingW_(M,n1)X_(n1), which is obtained by multiplying an orthogonal codesequence W_(M,n1) by first data group X_(n1) of a n-th block, andW_(M,n2)X_(n2), which is obtained by multiplying an orthogonal codesequence W_(M,n2) by second data group X_(n2) of a n-th block, M and nbeing positive integers; complex-multiplying the complex summed form ofW_(M,n1)X_(n1)+jW_(M,n2)X_(n2), by a complex form of W_(M,n3)+jW_(M,n4)and outputting (W_(M,n1)X_(n1)+jW_(M,n2)X_(n2))×(W_(M,n3)+jW_(M,n4)) asan output signal; and summing in-phase and quadrature phase parts of theoutput signal outputted from a plurality of blocks as$\left( {\sum\limits_{n = 1}^{K}\;\left( {\left( {{W_{M,{n\; 1}}X_{n\; 1}} + {\left( {jW} \right)_{M,{n\; 2}}X_{n\; 2}}} \right) \times \left( {W_{M,{n\; 3}} + \left( {jW} \right)_{M,,{n\; 4}}} \right)} \right)} \right),$ K is a predetermined integer greater than or equal to 1 to generate Ichannel and Q channel signal.
 2. The method of claim 1 wherein aspreading code spreads the summed in-phase and quadrature-phase signalsoutputted from the summing step.
 3. The method of claim 1 wherein saidorthogonal code sequence includes a Hadamard code sequence.
 4. Themethod of claim 1 wherein said orthogonal code sequence includes a Walshcode.
 5. The method of claim 2 wherein said spreading code is onespreading code.
 6. The method of claim 5 wherein said spreading codesequence includes a PN code.
 7. The method of claim 5 wherein saidspreading code includes a first spreading code for the in-phase signaland a second spreading code for the quadrature-phase signal.
 8. Themethod of claim 7 wherein the first and second spreading codes are PNcodes.
 9. The method of claim 3 wherein W_(M,11)=W₀, W_(M,12)=W₂, andW_(M,13)=W₀, W_(M,14)=W₁, when M=4.
 10. The method of claim 9 whereinM=8 and W_(M,12)=W₄.
 11. The method of claim 3 wherein W_(M,n1)=W₀,W_(M,n2)=W_(2p), where p represents a predetermined number in a rangefrom 0 to (M/2)−1, and W_(M,n3)=W_(2n-2), W_(M,n4)=W_(2n-1).
 12. Themethod of claim 3 wherein W_(M,21)=W₀, W_(M,22)=W₄, W_(M,23)=W₂,W_(M,24)=W₃ when M=8 in case of two channels.
 13. The method of claim 12wherein W_(M,12)=W₆, and W_(M,22)=W₆.
 14. An orthogonal complexspreading apparatus, comprising: a plurality of complex multiplicationblocks, each for complex-multiplexing a complex signalW_(M,n1)X_(n1)+jW_(M,n2)X_(n2) by W_(M,n3)+jW_(M,n4) whereinW_(M,n1)X_(n1) is obtained by multiplying an orthogonal code sequenceW_(M,n1) by first data group X_(n1) of n-th block and W_(M,n2)X_(n2) isobtained by multiplying orthogonal sequence W_(M,n2) by second datagroup X_(n2) of the n-th block, wherein M and n are positive integersand W_(M,n1), W_(M,n2), W_(M,n3) and W_(M,n4) are predeterminedorthogonal sequences; and a summing unit for summing in-phase andquadrature phase parts of an output signal from each block of theplurality of the complex multiplication blocks as$\left( {\sum\limits_{n = 1}^{K}\;\left( {\left( {{\alpha_{n\; 1}W_{M,{n\; 1}}X_{n\; 1}} + {{j\alpha}_{n\; 2}W_{M,{n\; 2}}X_{n\; 2}}} \right) \times \left( {W_{M,{n\; 3}} + \left( {jW} \right)_{M,,{n\; 4}}} \right)} \right)} \right),$ K is a predetermined integer greater than or equal to
 1. 15. Theapparatus of claim 14 further comprising a spreading unit formultiplying the summed in-phase and quadrature phase signals inputtedfrom the summing unit by spreading code.
 16. The apparatus of claim 15wherein said spreading unit multiplies the in-phase and quadrature phasepart by different spreading codes.
 17. The apparatus of claim 14 whereineach said complex multiplication block includes: a first multiplier formultiplying the first data group X_(n1) by the orthogonal code sequenceW_(M,n1); a second multiplier for multiplying the second data groupX_(n2) by the orthogonal code sequence W_(M,n2); third and fourthmultipliers for multiplying the output signal W_(M,n1)X_(n1) from thefirst multiplier and the output signal W_(M,n2)X_(n2) from the secondmultiplier by orthogonal code sequence W_(M,n3); fifth and sixthmultipliers for multiplying the output signal W_(M,n1)X_(n1) from thefirst multiplier and the output signal W_(M,n2)X_(n2) from the secondmultiplier by orthogonal code sequence W_(M,n4); a first adder forsubtracting output signal from the sixth multiplier from output signal(ac) from the third multiplier and outputting an in-phase information;and a second adder for summing output signal from the fourth multiplierand output signal from the fifth multiplier and outputting quadraturephase information.
 18. The apparatus of claim 17 wherein said orthogonalcode sequence includes a Hadamard code sequence.
 19. The apparatus ofclaim 17 wherein said orthogonal code sequence includes a Walsh code.20. A permuted orthogonal complex spreading method for multiple channelsallocating at least two input channels to first and second groups,comprising the steps of: multiplying a predetermined orthogonal codesequence W_(M,n1) by first data group X_(n1); multiplying orthogonalcode sequence W_(M,n2) by second data group X_(n2); summing outputsignals W_(M,n1)X_(n1) and W_(M,n2)X_(n2) in the complex form of${\sum\limits_{n = 1}^{K}\;\left( {{W_{M,{n\; 1}}X_{n\; 1}} + {\left( {jW} \right)_{M,{n\; 2}}X_{n\; 2}}} \right)};$ and complex-multiplying the received output signal$\sum\limits_{n = 1}^{K}{\left( {{W_{M,{n\; 1}}X_{n\; 1}} + {\left( {jW} \right)_{M,{n\; 2}}X_{n\; 2}}} \right)\mspace{14mu}{by}\mspace{14mu}\left( {W_{M,I} + \left( {j{PW}} \right)_{M,Q}} \right)}$ wherein P is a predetermined sequence, and W_(M,I) and W_(M,Q) areorthogonal code sequences.
 21. The method of claim 20 wherein thespreading code is a PN code.
 22. The method of claim 20 wherein Prepresents said predetermined sequence or predetermined spreading codeor predetermined integer configured so that two consecutive sequenceshave identical values.
 23. The method of claim 20 wherein saidorthogonal code sequence includes a Hadamard code sequence.
 24. Themethod of claim 20 wherein said orthogonal code sequence includes aWalsh code.
 25. The method of claim 23 wherein W_(M,I)=W₀,W_(M,Q)=W_(2q+1) (where q represents a predetermined number in a rangefrom 0 to (M/2)−1).
 26. The method of claim 23 further comprising thesteps of: multiplying the first data group X_(n1) by gain α_(n1); andmultiplying the second data group X_(n2) by gain α_(n2).
 27. The methodof claim 23 wherein W_(M,11)=W₀, W_(M,12)=W₂, and W_(M,I)=W₀,W_(M,Q)=W₁, where M=4.
 28. The method of claim 27 wherein M=8 andW_(M,12)=W₄.
 29. The method of claim 23 wherein W_(M,n1)=W₀,W_(M,n2)=W_(2q+1), wherein q represents a predetermined number in arange from 0 to (M/2)−1 and W_(M,I)=W₀, W_(M,Q)=W₁.
 30. The method ofclaim 20 wherein each group has at least two channels and the receivingstep includes the steps of: summing output signals W_(M,n1)X_(n1) from afirst sequence multiplier; and summing output signals W_(M,n2)X_(n2)from a second sequence multiplier.
 31. A permuted orthogonal complexspreading apparatus for multiple channels, allocating at least two inputchannels to first and second groups, comprising: a first multiplierblock having at least one channel contained in a first group ofchannels, each for outputting W_(M,n1)X_(n1) which is obtained bymultiplying first data group X_(n1) by orthogonal code sequenceW_(M,n1), M and n are positive integers; a second multiplier blockhaving a number of channels having at least one channel contained in asecond group of channels, each for outputting W_(M,n2)X_(n2) which isobtained by multiplying a first data group X_(n2) by orthogonal codesequence W_(M,n2); a complex multiplier for receiving the output signalsfrom the first and the second multiplier blocks in a complex form of$\sum\limits_{n = 1}^{K}\;\left( {{W_{M,{n\; 1}}X_{n\; 1}} + {\left( {jW} \right)_{M,{n\; 2}}X_{n\; 2}}} \right)$ and complex-multiplying received output signal by W_(M,I)+jPW_(M,Q),wherein W_(M,I) and W_(M,Q) are predetermined orthogonal code sequencepermuted and P is a predetermined sequence.
 32. The apparatus of claim31 wherein said orthogonal code sequence includes a Hadamard codesequence.
 33. The apparatus of claim 31 wherein said orthogonal codesequence includes a Walsh code.
 34. The apparatus of claim 32 whereinW_(M,11)=W₀, W_(M,12)=W₄, W_(M,21)=W₂, and W_(M,I)=W₀, W_(M,Q)=W₁, whenM=8 in case of three input channels.
 35. The apparatus of claim 32wherein W_(M,11)=W₀, W_(M,12)=W₂, and W_(M,I)=W₀, W_(M,Q)=W₁ in case ofthree input channels.
 36. The apparatus of claim 32 wherein W_(M,11)=W₀,W_(M,12)=W₄, W_(M,23)=W₂, W_(M,31)=W₆, and W_(M,I)=W₀, W_(M,Q)=W₁ incase of four input channels.
 37. The apparatus of claim 32 whereinW_(M,11)=W₀, W_(M,12)=W₄, W_(M,31)=W₂, W_(M,I)=W₀, W_(M,Q)=W₁ andW_(M,21)=W₆ in case of four input channels.
 38. The apparatus of claim32 wherein W_(M,11)=W₀, W_(M,12)=W₄, W_(M,21)=W₂, W_(M,31)=W₀,W_(M,22)=W₁, and W_(M,I)W₀, W_(M,Q)=W₁ in case of five input channels.39. The apparatus of claim 32 wherein W_(M,n1)=W₀, W_(M,12)=W₄,W_(M,21)=W₂, W_(M,31)=W₆, W_(M,22)=W₃, and W_(M,I)=W₀, W_(M,Q)=W₁ incase of five channels.
 40. The apparatus of claim 31 whereinW_(M,11)=W₀, W_(M,12)=W₄, W_(M,31)W₂, W_(M,22)=W₆, and W_(M,I)=W₀,W_(M,Q)=W₁ and W_(M,21)=W₈ in case of five input channels.
 41. Theapparatus of claim 36 wherein W₀X₁₁+jW₄X₁₂, W₂X₂₁ and W₆X₃₁ are replacedby α₁₁W₀X₁₁+jα₁₂W₄X₁₂, α₂₁W₂X₂₁ and α₃₁W₆X₃₁, and a gain α_(n1) and again α_(n2) are the identical gain in order to remove the phasedependency by an interference occurring in a multipath of a self signaland an interference occurring by other users.
 42. The apparatus of claim31 wherein W_(M,n1)=W₀, W_(M,n2)=W₂, and W_(M,I)=W₀, W_(M,Q)=W₁.
 43. Theapparatus of claim 31 wherein the first multiplier block comprises atleast a third multiplier for multiplying the first data group X_(n1) bygain α_(n1), and the second multiplier block comprises at least a fourthmultiplier the second data group X_(n2) by gain α_(n2).
 44. Theapparatus of claim 31 wherein W_(M,11)=W₀, W_(M,12)=W_(4/1), andW_(M,I)=W₀, W_(M,Q)=W_(1/4), when M=8 in case of two input channels. 45.The apparatus of claim 32 wherein W_(M,11)=W₀, W_(M,12)=W_(4/1),W_(M,21)=W₂, and W_(M,I)=W₀, W_(M,Q)=W_(1/4), when M=8 in case of threeinput channels.
 46. The method of claim 32 wherein W_(M,11)=W₀,W_(M,12)=W_(2/1), and W_(M,I)=W₀, W_(M,Q)=W_(1/2), when M=8 in case oftwo input channels.
 47. The apparatus of claim 32 wherein W_(M,11)=W₀,W_(M,12)=W_(2/1), W_(M,21)=W₄, and W_(M,I)=W₀, W_(M,Q)=W_(1/2), when M=8in case of three input channels.
 48. The apparatus of claim 31 whereineach group has at least the two input channels, further comprising: afirst adder for outputting$\sum\limits_{n = 1}^{K}\;\left( {W_{M,{n\; 1}}X_{n\; 1}} \right)$  bysumming output signals from the first multiplier block; and a secondadder for outputting$\sum\limits_{n = 1}^{K}\;\left( {W_{M,{n\; 2}}X_{n\; 2}} \right)$  bysumming output signals from the second multiplier block.
 49. Theapparatus of claim 31 further comprising: a spreading unit formultiplying the signal$\sum\limits_{n = 1}^{K}\;\left( {{W_{M,{n\; 1}}X_{n\; 1}} + {{jW}_{M,{n\; 2}}X_{n\; 2}}} \right)$ received by the complex multiplier by a spreading code.
 50. Theapparatus of claim 49 wherein the spreading unit respectively multipliesthe in-phase and quadrature-phase parts by different spreading codes.51. The apparatus of claim 31 wherein W_(M,n1), W_(M,n2), W_(M,I), andW_(M,Q) are orthogonal Hadamard sequences.
 52. The apparatus of claim 31wherein the complex multiplier includes: fifth and sixth multipliers formultiplying said output signal from the first multiplier block and saidoutput signal from the second sequence multiplier by orthogonal sequenceW_(M,I); seventh and eighth multipliers for multiplying said outputsignal from the first multiplier block and output signalα_(n2)W_(M,n2)X_(n2) from the second multiplier block by orthogonalsequence W_(M,Q); a third adder for subtracting output signal from theeighth multiplier from output signal from the fifth multiplier to outputan in-phase information; and a second adder for summing output signalfrom the sixth multiplier and output signal from the seventh multiplierto output quadrature-phase information.
 53. A permuted orthogonalcomplex spreading apparatus for multiple channels, allocating at leasttwo input channels into first and second groups, comprising: first andsecond multiplier blocks for respectively multiplying first and seconddata group X_(n1), and X_(n2) with a set of predetermined orthogonalsequences W_(M,n1), and W_(M,n2) to output W_(M,n1)X_(n1) andW_(M,n2)X_(n2); a complex multiplier for receiving the output signalsW_(M,n1)X_(n1) and W_(M,n2)X_(n2) from the first and the secondmultiplier blocks in the complex form of$\sum\limits_{n = 1}^{K}\;\left( {{W_{M,{n\; 1}}X_{n\; 1}} + {{jW}_{M,{n\; 2}}X_{n\; 2}}} \right)$ and multiplying a received signal$\sum\limits_{n = 1}^{K}\;\left( {{W_{M,{n\; 1}}X_{n\; 1}} + {{jW}_{M,{n\; 2}}X_{n\; 2}}} \right)$ by a predetermined sequence (W_(M,I)+jPW_(M,Q))×SC, wherein W_(M,I),W_(M,Q) are predetermined orthogonal sequences, P is a predeterminedsequence and SC is a spreading sequence.
 54. The apparatus of claim 53wherein each group has at least two input channels, further comprising:a first adder for outputting$\sum\limits_{n = 1}^{K}\;\left( {W_{M,{n\; 1}}X_{n\; 1}} \right)$  bysumming output signals from the first sequence multiplier; and a secondadder for outputting$\sum\limits_{n = 1}^{K}\;\left( {W_{M,{n\; 2}}X_{n\; 2}} \right)$  bysumming output signals from the second sequence multiplier.
 55. Theapparatus of claim 53 wherein the first sequence multiplier comprises atleast one first gain multiplier for multiplying the data X_(n1), of eachchannel of the first group by gain α_(n1), and the second sequencemultiplier comprises at least one second gain multiplier for multiplyingthe data X_(n2) of each channel of the second group by gain α_(n2). 56.The apparatus of claim 53 wherein W_(M,n1)=W₀, W_(M,n2)W_(2p), andW_(M,I)=W₀, W_(M,Q)=W₁, where p represents a predetermined integer in arange from 0 to (M/2)−1.
 57. The apparatus of claim 53 wherein W_(M,n1),W_(M,n2), W_(M,I), and W_(M,Q) are orthogonal Hadamard sequences.
 58. Amobile communications device, comprising: a first signal generatorconfigured to generate a first signal, a, based on at least a firstinput, a first code, and a first gain; a second signal generatorconfigured to generate a second signal, b, based on at least a secondinput, a second code, and a second gain; a first sequence receiving unitconfigured to receive a first sequence of elements, the elements in thefirst sequence of elements nonrandomly alternating between a first valueand a second value, the first value being different from the secondvalue; a second sequence receiving unit configured to receive a secondsequence of elements, e, wherein some of the elements in the secondsequence of elements have the first value and the other elements in thesecond sequence of elements have the second value; a first output unitconfigured to nonrandomly output e·a−e·b·d, wherein d is a third signalbased on at least the first sequence of elements; and a second outputunit configured to nonrandomly output e·b+e·a·d.
 59. The mobilecommunication device of claim 58, wherein the first sequence of elementsis W₁.
 60. The mobile communication device of claim 59, wherein thefirst signal is generated based on at least a fourth signal generated bymultiplying the first input, the first code, and the first gain, and thesecond signal is generated based on at least a fifth signal generated bymultiplying the second input, the second code, and the second gain. 61.The mobile communication device of claim 59, wherein the first codeconsists of elements, one or more of the elements of the first codehaving the first value and the remaining elements of the first codehaving the second value, wherein for the (2M−1)th element of the firstcode, the value of the (2M−1)th element of the first code is the same asthe value of the (2M)th element of the first code, where M is a seriesof sequential positive integers beginning at
 1. 62. The mobilecommunication device of claim 61, wherein the second code consists ofelements, one or more of the elements of the second code having thefirst value and the remaining elements of the second code having thesecond value, wherein for the (2K−1)th element of the second code, thevalue of the (2K−1)th element of the second code is the same as thevalue of the (2K)th element of the second code, where K is a series ofsequential positive integers beginning at
 1. 63. The mobilecommunication device of claim 59, wherein the first signal consists of asequence of pairs of elements, wherein each pair of elements consists oftwo elements both having a same value.
 64. The mobile communicationdevice of claim 63, wherein the second signal consists of a sequence ofpairs of elements, wherein each pair of elements consists of twoelements both having a same value.
 65. The mobile communication deviceof claim 58, wherein the second sequence of elements is a first PN code.66. The mobile communication device of claim 65, wherein the firstsequence of elements is W₁.
 67. The mobile communication device of claim65, wherein the third signal is further based on a third sequence ofelements.
 68. The mobile communication device of claim 58, wherein thethird signal is further based on a third sequence of elements.
 69. Themobile communication device of claim 68 or claim 67, wherein the thirdsequence of elements is generated based on a second PN code.
 70. Themobile communication device of claim 68 or claim 67, wherein the thirdsequence of elements is generated based on a spreading sequence.
 71. Themobile communication device of claim 68 or claim 67, wherein one or moreof the elements in the third sequence of elements have the first valueand the remaining elements in the third sequence of elements have thesecond value, wherein for the (2N−1)th element in the third sequence ofelements, the value of the (2N−1)th element is the same as the value ofthe (2N)th element in the third sequence of elements, where N is aseries of sequential positive integers beginning at
 1. 72. The mobilecommunication device of claim 68 or claim 67, wherein the third signalis a multiplication of the first sequence of elements and the thirdsequence of elements.
 73. The mobile communication device of claim 68 orclaim 67, wherein the third sequence of elements consists of a sequenceof groups, wherein each of the groups consists of either two elementsboth having the first value or two elements both having the secondvalue.
 74. The mobile communication device of claim 58, wherein thefirst signal is generated based on at least a fourth signal generated bymultiplying the first input, the first code, and the first gain, and thesecond signal is generated based on at least a fifth signal generated bymultiplying the second input, the second code, and the second gain. 75.The mobile communication device of claim 68 or claim 67, wherein thethird signal is a multiplication of the first sequence of elements andthe third sequence of elements and wherein the third sequence consistsof a sequence of groups, wherein each of the groups consists of eithertwo elements both having the first value or two elements both having thesecond value.
 76. The mobile communication device of claim 75, whereinthe first signal is generated based on at least a fourth signalgenerated by multiplying the first input, the first code, and the firstgain, and the second signal is generated based on at least a fifthsignal generated by multiplying the second input, the second code, andthe second gain.
 77. The mobile communication device of claim 76,wherein the first code consists of elements, one or more of the elementsof the first code having the first value and the remaining elements ofthe first code having the second value, wherein for the (2M−1)th elementof the first code, the value of the (2M−1)th element of the first codeis the same as the value of the (2M)th element of the first code, whereM is a series of sequential positive integers beginning at
 1. 78. Themobile communication device of claim 77, wherein the second codeconsists of elements, one or more of the elements of the second codehaving the first value and the remaining elements of the second codehaving the second value, wherein for the (2K−1)th element of the secondcode, the value of the (2K−1)th element of the second code is the sameas the value of the (2K)th element of the second code, where K is aseries of sequential positive integers beginning at
 1. 79. The mobilecommunication device of claim 76, wherein the first signal consists of asequence of pairs of elements, wherein each pair of elements consists oftwo elements both having a same value.
 80. The mobile communicationdevice of claim 79, wherein the second signal consists of a sequence ofpairs of elements, wherein each pair of elements consists of twoelements both having a same value.
 81. The mobile communication deviceof claim 75, wherein the first code consists of elements, one or more ofthe elements of the first code having the first value and the remainingelements of the first code having the second value, wherein for the(2M−1)th element of the first code, the value of the (2M−1)th element ofthe first code is the same as the value of the (2M)th element of thefirst code, where M is a series of sequential positive integersbeginning at
 1. 82. The mobile communication device of claim 81, whereinthe second code consists of elements, one or more of the elements of thesecond code having the first value and the remaining elements of thesecond code having the second value, wherein for the (2K−1)th element ofthe second code, the value of the (2K−1)th element of the second code isthe same as the value of the (2K)th element of the second code, where Kis a series of sequential positive integers beginning at
 1. 83. Themobile communication device of claim 75, wherein the first signalconsists of a sequence of pairs of elements, wherein each pair ofelements consists of two elements both having a same value.
 84. Themobile communication device of claim 83, wherein the second signalconsists of a sequence of pairs of elements, wherein each pair ofelements consists of two elements both having a same value.
 85. Themobile communication device of claim 58 or claim 65, wherein the firstcode and the second code include Walsh codes.
 86. The mobilecommunication device of claim 58 or claim 65, wherein the first code andthe second code are even-numbered Walsh codes.
 87. The mobilecommunication device of claim 86, wherein the first signal is generatedbased on at least a fourth signal generated by multiplying the firstinput, the first code, and the first gain, and the second signal isgenerated based on at least a fifth signal generated by multiplying thesecond input, the second code, and the second gain.
 88. The mobilecommunication device of claim 68, wherein the first signal is generatedbased on at least a fourth signal generated by multiplying the firstinput, the first code, and the first gain, and the second signal isgenerated based on at least a fifth signal generated by multiplying thesecond input, the second code, and the second gain.
 89. The mobilecommunication device of claim 58, wherein the first code consists ofelements, one or more of the elements of the first code having the firstvalue and the remaining elements of the first code having the secondvalue, wherein for each (2M−1)th element of the first code, the value ofthe (2M−1)th element of the first code is the same as the value of a(2M)th element of the first code, where M is a series of sequentialpositive integers beginning at
 1. 90. The mobile communication device ofclaim 89, wherein the second code consists of elements, one or more ofthe elements of the second code having the first value and the remainingelements of the second code having the second value, wherein for the(2K−1)th element of the second code, the value of the (2K−1)th elementof the second code is the same as the value of the (2K)th element of thesecond code, where K is a series of sequential positive integersbeginning at
 1. 91. The mobile communication device of claim 58, whereinthe first signal consists of a sequence of pairs of elements, whereineach pair of elements consists of two elements both having a same value.92. The mobile communication device of claim 91, wherein the secondsignal consists of a sequence of pairs of elements, wherein each pair ofelements consists of two elements both having a same value.
 93. Themobile communication device of claim 58, wherein the second sequence ofelements is a spreading sequence.
 94. A mobile communications device,comprising: a first output generator configured to generate a firstoutput, a, based on at least one or more first inputs, one or more firstcodes, and one or more first gains; a second output generator configuredto generate a second output, b, based on at least one or more secondinputs, one or more second codes, and one or more second gains; a firstsequence receiving unit configured to receive a first sequence ofelements, e, wherein some of the elements in the first sequence have afirst value and the other elements in the first sequence have a secondvalue, the first value being different from the second value; a secondsequence receiving unit configured to receive a second sequence ofelements, W; a third sequence receiving unit configured to receive athird sequence of elements, P; and an output unit configured tononrandomly output (a+jb)·(1+jP·W)·e.
 95. The mobile communicationdevice of claim 94, wherein the second sequence of elements is W₁. 96.The mobile communication device of claim 95, wherein: the first outputis generated based on summing one or more first multiplications, eachfirst multiplication generated by multiplying one of the one or morefirst inputs, one of the one or more first codes, and one of the one ormore first gains; and the second output is generated based on summingone or more second multiplications, each second multiplication generatedby multiplying one of the one or more second inputs, one of the one ormore second codes, and one of the one or more second gains.
 97. Themobile communication device of claim 96, wherein: each of the one ormore first codes consists of elements; for each of the one or more firstcodes, one or more of the elements in the respective first code have thefirst value and the remaining elements have the second value; and forthe (2M−1)th element of each of the one or more first codes, the valueof the (2M−1)th element is the same as the value of the (2M)th element,where M is a series of sequential positive integers beginning at
 1. 98.The mobile communication device of claim 97, wherein: each of the one ormore second codes consists of elements; for each of the one or moresecond codes, one or more of the elements in the respective second codehave the first value and the remaining elements have the second value;and for the (2K−1)th element of each of the one or more second codes,the value of the (2K−1)th element is the same as the value of the (2K)thelement, where K is a series of sequential positive integers beginningat
 1. 99. The mobile communication device of claim 96, wherein the firstoutput consists of a sequence of pairs of elements, wherein each pair ofelements consists of two elements both having a same value.
 100. Themobile communication device of claim 99, wherein the second outputconsists of a sequence of pairs of elements, wherein each pair ofelements consists of two elements both having a same value.
 101. Themobile communication device of claim 95, wherein: each of the one ormore first codes consists of elements; for each of the one or more firstcodes, one or more of the elements in the respective first code have thefirst value and the remaining elements have the second value; and forthe (2M−1)th element of each of the one or more first codes, the valueof the (2M−1)th element is the same as the value of the (2M)th element,where M is a series of sequential positive integers beginning at
 1. 102.The mobile communication device of claim 101, wherein: each of the oneor more second codes consists of elements; for each of the one or moresecond codes, one or more of the elements in the respective second codehave the first value and the remaining elements have the second value;and for the (2K−1)th element of each of the one or more second codes,the value of the (2K−1)th element is the same as the value of the (2K)thelement, where K is a series of sequential positive integers beginningat
 1. 103. The mobile communication device of claim 95, wherein thefirst output consists of a sequence of pairs of elements, wherein eachpair of elements consists of two elements both having a same value. 104.The mobile communication device of claim 103, wherein the second outputconsists of a sequence of pairs of elements, wherein each pair ofelements consists of two elements both having a same value.
 105. Themobile communication device of claim 94, wherein the one or more firstcodes and the one or more second codes are even-numbered Walsh codes.106. The mobile communication device of claim 105, wherein: the firstoutput is generated based on summing one or more first multiplications,each first multiplication generated by multiplying one of the one ormore first inputs, one of the one or more first codes, and one of theone or more first gains; and the second output is generated based onsumming one or more second multiplications, each second multiplicationgenerated by multiplying one of the one or more second inputs, one ofthe one or more second codes, and one of the one or more second gains.107. The mobile communication device of claim 94, wherein the (2N−1)thelement in the second sequence of elements has the first value and the(2N)th element in the second sequence of elements has the second value,wherein N is a series of sequential positive integers beginning at 1.108. The mobile communication device of claim 107, wherein: the firstoutput is generated based on summing one or more first multiplications,each first multiplication generated by multiplying one of the one ormore first inputs, one of the one or more first codes, and one of theone or more first gains; and the second output is generated based onsumming one or more second multiplications, each second multiplicationgenerated by multiplying one of the one or more second inputs, one ofthe one or more second codes, and one of the one or more second gains.109. The mobile communication device of claim 107, wherein: each of theone or more first codes consists of elements; for each of the one ormore first codes, one or more of the elements in the respective firstcode have the first value and the remaining elements have the secondvalue; and for the (2M−1)th element of each of the one or more firstcodes, the value of the (2M−1)th element is the same as the value of the(2M)th element, where M is a series of sequential positive integersbeginning at
 1. 110. The mobile communication device of claim 109,wherein: each of the one or more second codes consists of elements; foreach of the one or more second codes, one or more of the elements in therespective second code have the first value and the remaining elementshave the second value; and for the (2K−1)th element of each of the oneor more second codes, the value of the (2K−1)th element is the same asthe value of the (2K)th element, where K is a series of sequentialpositive integers beginning at
 1. 111. The mobile communication deviceof claim 107, wherein the first output consists of a sequence of pairsof elements, wherein each pair of elements consists of two elements bothhaving a same value.
 112. The mobile communication device of claim 111,wherein the second output consists of a sequence of pairs of elements,wherein each pair of elements consists of two elements both having asame value.
 113. The mobile communication device of claim 94, claim 95,claim 105, or claim 107, wherein the third sequence of elements consistsof a sequence of groups, wherein each of the groups consists of eithertwo elements both having the first value or two elements both having thesecond value.
 114. The mobile communication device of claims 94, claim95, claim 105, or claim 107, wherein P is generated based on a PN code.115. The mobile communication device of claim 94, claim 95, claim 105,or claim 107, wherein e is a spreading sequence.
 116. The mobilecommunication device of claim 94, claim 95, claim 105, or claim 107,wherein e is a PN code.
 117. The mobile communication device of claim94, wherein: the first output is generated based on summing one or morefirst multiplications, each first multiplication generated bymultiplying one of the one or more first inputs, one of the one or morefirst codes, and one of the one or more first gains; and the secondoutput is generated based on summing one or more second multiplications,each second multiplication generated by multiplying one of the one ormore second inputs, one of the one or more second codes, and one of theone or more second gains.
 118. The mobile communication device of claim117, wherein: each of the one or more first codes consists of elements;for each of the one or more first codes, one or more of the elements inthe respective first code have the first value and the remainingelements have the second value; and for the (2M−1)th element of each ofthe one or more first codes, the value of the (2M−1)th element is thesame as the value of the (2M)th element, where M is a series ofsequential positive integers beginning at
 1. 119. The mobilecommunication device of claim 118, wherein: each of the one or moresecond codes consists of elements; for each of the one or more secondcodes, one or more of the elements in the respective second code havethe first value and the remaining elements have the second value; andfor the (2K−1)th element of each of the one or more second codes, thevalue of the (2K−1)th element is the same as the value of the (2K)thelement, where K is a series of sequential positive integers beginningat
 1. 120. The mobile communication device of claim 117, wherein thefirst output consists of a sequence of pairs of elements, wherein eachpair of elements consists of two elements both having a same value. 121.The mobile communication device of claim 120, wherein the second outputconsists of a sequence of pairs of elements, wherein each pair ofelements consists of two elements both having a same value.
 122. Themobile communication device of claim 94, wherein: each of the one ormore first codes consists of elements; for each of the one or more firstcodes, one or more of the elements in the respective first code have thefirst value and the remaining elements have the second value; and forthe (2M−1)th element of each of the one or more first codes, the valueof the (2M−1)th element is the same as the value of the (2M)th element,where M is a series of sequential positive integers beginning at
 1. 123.The mobile communication device of claim 122, wherein: each of the oneor more second codes consists of elements; for each of the one or moresecond codes, one or more of the elements in the respective second codehave the first value and the remaining elements have the second value;and for the (2K−1)th element of each of the one or more second codes,the value of the (2K−1)th element is the same as the value of the (2K)thelement, where K is a series of sequential positive integers beginningat
 1. 124. The mobile communication device of claim 94, wherein thefirst output consists of a sequence of pairs of elements, wherein eachpair of elements consists of two elements both having a same value. 125.The mobile communication device of claim 124, wherein the second outputconsists of a sequence of pairs of elements, wherein each pair ofelements consists of two elements both having a same value.